## A Generalized Proportional Integral Output Feedback Controller for the Robust Perturbation Rejection in a Mechanical System

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1 A Generalized Proportional Integral Output Feedback Controller for the Robust Perturbation Rejection in a Mechanical System Hebertt Sira-Ram´ırez †, Francisco Beltr´an-Carbajal ‡ and Andr´es Blanco-Ortega ‡. Abstract—In this article, a Generalized Proportional Integral (GPI) controller is proposed for the efﬁcient rejection of a completely unknown perturbation input in a controlled mass system attached to an uncertain mass-spring-damper mechanical system. We propose a classical compensation network form of the GPI controller, including a sufﬁcient number of extra integra- tions, which results in a robust perturbation rejection scheme for a trajectory tracking task on the controlled mass subject to the unknown perturbation input. Aside from encouraging simulations, the proposed controller is implemented and tested in a laboratory experimental set up and its robust performance is clearly assessed by using exactly the same controller in three completely different topological situations. The experiments are repeated including inﬁnite dimensional perturbations arising from the effects of several added un-modeled ﬂexible appendages carrying unknown masses. Index Terms—GPI control, Perturbation Rejection, Flatness. I. INTRODUCTION Generalized Proportional Integral (GPI) control was intro- duced, in the context of Predictive Control of Differentially Flat systems in an article by Fliess and his coworkers [8]. The main idea is to avoid the explicit use of state observers by resorting to structural reconstructions of the state on the basis of iterated integrations of inputs and outputs. The method purposefully ignores initial conditions and classical perturba- tion inputs (constant perturbations, ramps, quadratic pertur- bations, etc., i.e., it ignores possibly unstable time-polynomial perturbations). Later on, still at the controller design stage, the method proposes a compensation of the effect of the neglected perturbations and initial conditions -in the state reconstruction task- by adding to the reconstructed state feedback controller a suitable linear combination of iterated output tracking error integrals. GPI controllers for state space described linear systems have been systematically derived in Fliess, M´arquez and Delaleau [7]. For time-varying linear systems and some applications in nonlinear Power Electronics we refer the reader to the work of Sira-Ram´ırez and Silva-Navarro [15] and [16]. In the context of nonlinear systems GPI controllers have been proposed, for the regulation of rigid and ﬂexible robots as well as inertia pendulum wheels, by Hern´andez and Sira-Ram´ırez in [10], [11], [12]. In the context of active vibration absorbers, GPI controllers have been previously addressed in the work of † H. Sira-Ram´ırez is with the Centro de Investigaci´on y Estudios Avanzados del IPN (Cinvestav-IPN), Mexico D.F., Mexico (e-mail: hsira@cinvestav.mx) ‡ F. Beltr´an-Carbajal and A. Blanco-Ortega are with the Instituto Tec- nol´ogico de Estudios Superiores de Monterrey, Campus Guadalajara, Guadala- jara, Jalisco (e-mail: francisco.beltran, andres.blanco@itesm.mx). Beltr´an et al (See [2]). Combinations of GPI controllers and fast algebraic identiﬁcation techniques for adaptive attenuation of vibrations may be found in Beltr´an et al. [3], and in [4]. GPI controllers merge quite well with sliding mode control techniques making it unnecessary to know the full state of the system, as evidenced in Beltr´an et al. [5]. GPI controllers have been used in several experimental set ups of power electronics problems in the works of Sira-Ram´ırez and Silva- Ortigoza [14] and more recently, for multivariable cases, in the work Franco et al. [9]. GPI controllers have been found to be expressible in proper transfer function form, or in classical compensation network form, in an article by Becedas et al. [1], where extensive experimental tests were successfully carried out, for controlling highly ﬂexible manipulators using a combination of GPI controllers and algebraic identiﬁcation techniques as advocated in Fliess and Sira-Ram´ırez in [6]. For other developments concerning GPI control of ﬂexible structures, see also Trapero et al. [17]. It is in this latter form, of classical compensation networks, that the greatest advantages of GPI control techniques emerge as related to controller simplicity, ease of implementation, reliability and numerical precision. In this article, we consider a mass, capable of sliding along horizontal guidelines, and controlled by an external input force. The mass is attached to a train of similar, but unknown, sliding masses joined in cascade by springs of unknown values. The number of masses affecting the motions of the directly controlled mass is completely unknown as it is unknown whether or not the very ﬁrst and the very last masses of the train system are free or are they attached to some ﬁxed point. We propose an output feedback controller of the GPI type, for a reference trajectory tracking task, which is based on position measurements of the controlled mass alone. The proposed controller is robust with respect to the perturbation force acting on the ﬁrst controlled mass as a result of the vibrations of the rest of the uncertain cascaded mass- spring-damper system and the spring and damper possibly attaching the mass to a ﬁxed point. In order to assess the performance and outstanding disturbance rejection capabilities of the proposed robust GPI controller, we also carry out the same previous experiments including one, two and three, vertical ﬂexible appendages attached to the moving masses with a mass placed at the free end of the appendage. Our GPI control design rationale is as follows: We ﬁrst design an output feedback trajectory tracking controller of the GPI type for the controlled mass which is made robust e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 2 with respect to an entire family of p − 1-th order unknown polynomial perturbation inputs. Clearly, any representative of such a polynomial input family is unbounded as long as its order is higher or equal than 1. Thanks to the internal model principle, the resulting output feedback controller, will exhibit p integrators and, in order to overcome the unstable perturba- tion input it has to, itself, exhibit an unstable behavior while being successful at quenching the tracking error asymptotically exponentially to zero. We next ask ourselves the following question: What is the nature of the closed loop response, and of the controller behavior, when we use the previously designed (potentially unstable) controller on a perturbed system whose perturbation input is no longer an unstable time polynomial signal but a bounded, sufﬁciently smooth, possibly state- dependent input signal? Since the controller is now facing a bounded perturbation which only locally looks like the previ- ously hypothesized polynomial input, the resulting controller must be still successful in producing a bounded tracking error response which is close to zero but, also, the controller output will no longer be an unbounded signal but a bounded one. This is due to the fact that the closed loops system is made into a linear exponentially asymptotically stable system processing a bounded residual signal representing the small difference between the actual bounded input and the hypothesized local polynomial approximation at the end of the “moving window” of validity of the polynomial approximation. Section 2 formulates the problem treated in this article. In this section we solve the closely related problem of designing an output feedback controller, for a single controlled mass, which asymptotically rejects an unstable time-polynomial ad- ditive perturbation input while tracking a given output refer- ence trajectory. In section 2 we also justify the boundedness of the closed loop performance of the previously designed output feedback controller when the additive perturbation input is no longer a time-polynomial signal but a bounded, sufﬁciently smooth, perturbation input signal. Section 3 presents a direct application of the above result to the problem of robustly regulating a sliding mass perturbed by an unknown interaction with an uncertain number of sliding masses attached to the regulated mass in a cascade, tandem, connection using springs with unknown coefﬁcients. Each unknown connected mass will also exhibit a damper modeling the viscous friction existing over the guidelines. The simulation results, presented in this section, motivated the testing of the control scheme on an experimental laboratory set up. We describe and report the successful experimental results in Section 4 where we also include experiments with unknown vibrating ﬂexible attach- ments. Section 5 contains the conclusions and suggestions for further research. II. PROBLEM FORMULATION Consider the mass-spring-damper system shown in Figure 1. Suppose this “train” of masses, sprigs and dampers is constituted, after the ﬁrst, actuated, known mass m, by an x2 xn c1 k1 k2 c2 k3 m1 m2 mn kn cn kn+1 cn+1c3 x1 Fig. 1. Mass-spring-damper system. uncertain number of connected masses. In other words, we do not know how many masses are there in the train attached to the ﬁrst mass, nor do we know whether or not the last mass in the train is attached to a wall and, moreover, we do not even know the values of the masses, springs stiffness coefﬁcients and dampers viscous friction coefﬁcients connecting any two consecutive masses beyond the ﬁrst one. Notice that such an unknown perturbation is, strictly speaking, a state dependent perturbation since the position and the velocity of the ﬁrst mass contribute to conform the unknown perturbation input. In spite of this, considering the dynamic perturbation as an unknown time signal will produce a successful and quite robust GPI controller. It is desired to obtain a feedback controller, based only on the measurement of the position variable, x, of the directly actuated mass, so that this ﬁrst mass position is accurately controlled to follow a given reference trajectory x∗ (t), in spite of the nature of the uncertain subsystem, attached through a spring and a damper to this ﬁrst mass, and acting as a perturbation input force of completely unknown nature. We reduce the posed problem to the following one: Given the following perturbed second order system: m¨x = u + ξ(t) where m is the known value of the mass, u is the externally applied control input force, the signal ξ(t) is the total, bounded and sufﬁciently smooth, perturbation force exercised by the motions of the uncertain train system affecting the controlled motions of the single mass system, devise a robust output feedback controller for u which causes the mass position, x, to track a given reference position trajectory x∗ (t), within a possible tracking error, x − x∗ (t), taking values in a small neighborhood of zero, in spite of the perturbation input values. A. An introductory related problem Consider the following related problem: Given a second order perturbed system m¨x = u + ξ(t) control x to track a given smooth reference trajectory x∗ (t) irrespectively of the coefﬁcient values of the ﬁnite p − 1-th order time polynomial signal ξ(t) i.e., ξ(t) = p−1 i=0 γiti e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 3 Although this is quite an unrealistic problem, given that any polynomial signal necessary grows without bound as t grows, it will require of a feedback controller action whose output signal, u, will also grow in a polynomial fashion. Nevertheless, and in spite of this unstable behavior, let us proceed to synthesize a controller for which the tracking error e = x − x∗ (t) exponentially asymptotically decreases to zero, even if at the costly expense of the internal feedback controller instability. We proceed as follows: Consider the nominal unperturbed system: m¨x∗ (t) = u∗ (t) the tracking error e = x − x∗ (t) evolves according to the perturbed dynamics m¨e = eu + ξ(t) with eu = u−u∗ (t). Since ξ(t) is a p−1-th order polynomial, its annihilator is constituted by the differential operator sp . We obtain, after taking p time derivatives on the tracking error system, the following expression for the evolution of e: me(p+2) (t) = e(p) u (t) = ev(t) where ev(t) = v − v∗ (t) is an auxiliary control input error representing the p-th order derivative of the original control input u. Notice that, v∗ (t) = m[x∗ (t)](p+2) . An output feedback controller for v which guarantees asymptotic exponential stabilization of the tracking error e to zero is given by the following GPI controller, written in classical compensation network form, where, in its expression, we have abusively combined time domain quantities with frequency domain quantities, as it is customary in many areas of modern automatic control: v = v∗ (t) − m kp+1sp+1 + kpsp + · · · + k1s + k0 sp+1 + k2p+2sp + · · · + kp+3s + kp+2 e(t) The closed loop tracking error system is seen to evolve, after some algebraic manipulations, as governed by the following symbolic representation of a 2p + 3-th homogeneous ordinary differential equation for the tracking error e = x − x∗ (t): s2p+3 + k2p+2s2p+2 + · · · + kp+2sp+2 +kp+1sp+1 + · · · + k1s + k0 e = 0 Clearly, the proper choice of the control network coefﬁcients {k2p+2, · · · , k1, k0}, representing also the coefﬁcients of the closed loop characteristic polynomial, as those of a Hurwitz polynomial, results in a globally exponentially asymptotically stable equilibrium point, e = 0, at the origin of the tracking error system space. The controller for the original input u is, according to the relation between u and the auxiliary control input v, given by: u = u∗ (t) − mG(s)(x − x∗ (t)) with G(s) = kp+1sp+1 + kpsp + · · · + k1s + k0 sp (sp+1 + k2p+2sp + · · · + kp+3s + kp+2) The following elementary magnitude check on the closed loop controlled system me(2) = eu + ξ(t) leads us to conclude that the controller output eu is to be regarded as an unbounded signal. Indeed, since e exponen- tially asymptotically decreases to zero, while ξ(t), due to its polynomial character, either grows to plus inﬁnity (when p−1 is even) or to minus inﬁnity (whenever p − 1 is odd), then, necessarily eu will counteract the growing perturbation at the expense of its own stability. i.e., eu, respectively, grows to either minus inﬁnity or to plus inﬁnity so that the signal e, and its time derivatives, remain bounded and decreasing to zero. B. Some natural questions and their answers The natural questions to be asked are the following: What happens to the tracking error e, and to the controller behav- ior, when the perturbation input signal, ξ(t), is no longer an unbounded polynomial input but a bounded, sufﬁciently smooth, perturbation input signal, and we still insist in using the previously designed output feedback controller G(s)? Will the controller output eu still behave in an unstable fashion or will it result in a bounded control input error?. The answer to these questions are: The designed output tracking feedback controller, which is ready to sustain asymp- totic stability of the controlled system when subject to an unstable input, will be now processing a bounded perturbation input which will not cause the control input to grow in a polynomial fashion. We have “fooled” the controller making it ready to control a polynomial perturbed system while, actually, the forseen unstable perturbation never shows up. Moreover, since the actual bounded smooth perturbation, locally in time, looks like any one of the representatives of the polynomial family with respect to which the controller has been made to act robustly, the controller effect is to try to regulate to zero, at every moment, the tracking error. Since the actual perturbation differs only slightly from one of the members of the annihilated polynomial family, the closed loop system is only affected by the residual perturbation input comprising the difference between the assumed polynomial input and the actual smooth, bounded, perturbation input. The net result is that the closed loop system, which has been made to be an asymptotically exponentially stable linear system, is in fact locally perturbed by a small bounded perturbation signal which is continuously obtained from the residual difference signal between a bounded signal and its locally approximating polynomial. The tracking of the given trajectory will be accomplished in an approximate manner with a tracking error signal uniformly living inside a small radius ball centered at the origin of the tracking error state space. C. Some motivating simulations In order to graphically evaluate our previous reasoning, sup- pose we would like to stabilize to, say, zero the output, y = x, of the second order perturbed system: m¨x = u+ξ(t) with ξ(t) being a polynomial input of, say, fourth degree. We thus have e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 4 x∗ (t) = 0 for all t and correspondingly, u∗ (t) = 0. Clearly, ﬁve time derivatives of the system expression annihilate the polynomial perturbation input, xi(t). We use the following GPI controller u = −m k6s6 + k5s5 + · · · + k1s + k0 s6 + k12s5 + · · · + k8s + k7 x The closed loop characteristic polynomial is simply given by p(s) = s13 + k12s12 + · · · + k1s + k0 Equating term by term, the coefﬁcients of the closed loop characteristic polynomial with the corresponding ones of the following Hurwitz polynomial: pd(s) = (s2 + 2ζωns + ω2 n)6 (s + p) we obtain the required controller gains {k12, k11, · · · , k1, k0} as follows: k12 = p + 12ζωn k11 = 12ζωnp + 60ζ2 ω2 n + 6ω2 n k10 = 6ω2 np + 160ζ3 ω3 n + 60ζ2 ω2 np + 60ζω3 n k9 = 240ζ2 ω4 n + 240ζ4 ω4 n + 15ω4 n + 160ζ3 ω3 np +60ζω3 np k8 = 120ζω5 n + 192ζ5 ω5 n + 240ζ4 ω4 np + 480ζ3 ω5 n +15ω4 np + 240ζ2 ω4 np k7 = 360ζ2 ω6 n + 480ζ4 ω6 n + 120ζω5 np + 64ζ6 ω6 n +192ζ5 ω5 np + 20ω6 n + 480ζ3 ω5 np k6 = 20ω6 np + 64ζ6 ω6 np + 120ζω7 n + 480ζ4 ω6 np +360ζ2 ω6 np + 480ζ3 ω7 n + 192ζ5 ω7 n k5 = 192ζ5 ω7 np + 480ζ3 ω7 np + 120ζω7 np + 240ζ2 ω8 n +240ζ4 ω8 n + 15ω8 n k4 = 160ζ3 ω9 n + 60ζω9 n + 15ω8 np + 240ζ4 ω8 np +240ζ2 ω8 np k3 = 60ζ2 ω10 n + 60ζω9 np + 6ω10 n + 160ζ3 ω9 np k2 = 6ω10 n p + 12ζω11 n + 60ζ2 ω10 n p k1 = ω12 n + 12ζω11 n p k0 = ω12 n p For the simulation results shown below we used the follow- ing data for the plant and the controller m = 1, ζ = 4, ωn = 20, p = 20, The polynomial input was set to be a fourth degree poly- nomial given by: ξ(t) = γ0 + γ1t + γ2t2 + γ3t3 + γ4t4 with γi = 1.0 × 10−3 for all i1 . Clearly, as the polynomial perturbation ξ(t) grows, the con- trol input u grows in the opposite direction canceling out the 1The only reason we have chosen a small factor for the polynomial per- turbation is to avoid large signals in the simulated controller output response which misses the details of how it opposes the polynomial perturbation input signal 0 1 2 3 4 5 6 7 8 −1 0 1 x 10 −4 0 1 2 3 4 5 6 7 8 −5 0 5 0 1 2 3 4 5 6 7 8 −5 0 5 x(t) u(t)u(t) u(t) ξ(t) Fig. 2. Closed loop response of polynomial perturbed second order system clearly exhibiting the canceling effect of the unstable control input. perturbation effect on the closed loop controlled system. The output signal x is seen to converge to zero in an asymptotically exponential fashion. The following ﬁgure depicts the performance of exactly the same feedback controller designed above when the per- turbation signal ξ(t) is given by a sufﬁciently smooth but bounded signal. We used the following perturbation input in the simulations ξ(t) = γ sin(t) exp(− sin2 (3t)), γ = 1.0 × 10−3 0 1 2 3 4 5 6 7 8 −1 0 1 x 10 −4 0 1 2 3 4 5 6 7 8 −2 0 2 x 10 −3 0 1 2 3 4 5 6 7 8 −2 0 2 x 10 −3 x(t) u(t) u(t) ξ(t) Fig. 3. Closed loop response of, bounded, non-polynomial perturbed second order system depicting the canceling effect of the bounded control input. The output signal x converges now to the interior of a small radius ball centered around the origin of the error space, while e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 5 the controller output u remains bounded only approximately canceling the effects of the smooth, bounded, perturbation input ξ(t). The approximate opposite nature of the control input with respect to the bounded perturbation input is clearly due to the simple magnitude balance in the system dynamics: m¨x = u+ξ(t). Indeed, now x(t) converges to a small vicinity around zero, and its ﬁrst and second order time derivatives remain bounded. It follows that, necessarily, u and ξ(t), nearly “point-wise” cancel each other in the sum, u + ξ(t), on the right hand side of the system dynamics. D. Main Result Theorem 1: Consider the perturbed system: m¨x = u + ξ(t) with m being the known mass, u is the externally applied force acting as a control input and let ξ(t) be an uniformly bounded, sufﬁciently smooth signal such that, given any integer p > 1, ξ(t) can be written as follows: ξ(t) = ξ0 + ξ1t + 1 2! ξ2t2 + · · · + 1 (p − 1)! ξp−1tp−1 + op(t) with ξi = di ξ(t) dti t=0 , i = 0, 1, · · · , p − 1 and |op(t)| is a bounded signal uniformly contained within a disk of small radius ǫp centered at the origin with op(0) = ˙op(0) = ... = 0. Given a smooth, desired, reference trajectory, x∗ (t), for the controlled position x, the robust GPI feedback controller including p extra integrations: u = u∗ (t)−m kp+1sp+1 + · · · + k1s + k0 sp(sp+1 + k2p+2sp + · · · + kp+2) (x−x∗ (t)) with u∗ (t) = m¨x∗ (t) being the nominal input of the sec- ond order mass system, globally asymptotically exponentially stabilizes the position tracking error e = x − x∗ (t), for the closed loop perturbed system, towards the interior of a small neighborhood of zero, provided the set of coefﬁcients {k2p+2, k2p+1, · · · , k1, k0} of the output GPI feedback track- ing controller are chosen so that the closed loop characteristic polynomial, pcl(s), is a Hurwitz polynomial given by, pcl(s) = s2p+3 + k2p+2s2p + · · · + kp+2sp+2 +kp+1sp+1 + · · · + k1s + k0 Proof Let e(t) = x − x∗ (t) and let pcl( d dt ) denote the differential polynomial obtained from pcl(s) after letting s = d dt . Consider the closed loop system in the time domain. We have after some elementary manipulations: pcl( d dt )e(t) = p+1 j=0 k2p+3−j d 2p+1−j dt 2p+1−j op(t) with k2p+3 = 1. Clearly, under the hypothesis of a small residual, op(t), in the vicinity of the current time t, the above equation represents an asymptotically exponentially stable system perturbed by a smooth, uniformly bounded signal of very small amplitude. By well known results, (See, for instance the excellent book by Rugh [13]) the closed loop tracking error response trajectory, e(t), remains uniformly bounded by a small radius disk centered around the origin. The robustness result follows. III. SIMULATION RESULTS We simulated the following mechanical system which co- incided with the topology of the experimental set up, m1 ¨x1 = u + ξ(t) ξ(t) = −k1x1 − c1 ˙x1 − k2(x1 − x2) m2 ¨x2 = −k2(x2 − x1) − c2 ˙x2 − k3(x2 − x3) m3 ¨x3 = −k3(x3 − x2) − c ˙x3 The unknown state-dependent perturbation input ξ(t) was modeled as a fourth order time polynomial 2 . A trajectory tracking task was adopted to have the controlled mass position x track, a B´ezier polynomial smoothly interpolating between zero and a ﬁnal position located at one centimeter from the initial rest position in approximately 3 [sec]. The controller was set to be: u = u∗ (t)−m k6s6 + k5s5 + · · · + k1s + k0 s5(s6 + k12s5 + · · · + k8s + k7) (x−x∗ (t)) The controller gains {k12, ...k0} were set to coincide with those of the desired characteristic polynomial (s2 + 2ζωns + ω2 n)6 (s + p) with ζ = 7, ωn = 60, p = 60. The various coefﬁcients were set to be approximately those of the experimental system: k1 = 525.25 [N/m], m1 = 2.78 [Kg], c1 = 3.8122 [N − s/m] k2 = 328.34 [N/m], m2 = 2.56 [Kg], c2 = 1.11 [N − s/m] k3 = 185.69 [N/m], m3 = 2.56 [Kg], c3 = 1.11 [N − s/m] IV. EXPERIMENTAL RESULTS A. Perturbation input arising from a ﬁnite dimensional system The following picture depicts the experimental ECP sys- tem on which we tested the proposed output feedback tracking control strategy of the GPI type with disturbance rejection fea- tures based on iterated integrations arising from a polynomial perturbation model annihilation via repeated differentiations of the simpliﬁed input output relation. 2Clearly, one can take the bounded time perturbation to be state dependent, in this case, because we know that the neglected contribution of the state function, considered as part of the unknown perturbation, still produces a stable system. Unknown expressions of the state which cause unstable open loop behavior must, in general, be known and exactly canceled on line. e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 6 0 1 2 3 4 5 0 0.005 0.01 0 1 2 3 4 5 0 5 0 1 2 3 4 5 −5 0 x(t),x*(t) u(t) ξ(t) Fig. 4. Simulated closed loop response of a robust GPI controlled mass position undergoing a state-dependent dynamic, bounded, perturbation. Fig. 5. Experimental ECP laboratory set up of mass-spring-damper system. We ﬁrst run the tracking controller when no masses were attached to the ﬁrst controlled mass. Figure 6 shows the obtained closed loop response. We then run the experiment again using exactly the same controller as before, but, this time, with only one (unknown) mass attached to the controlled system. The corresponding closed loop responses are shown in Figure 7. Finally, we run a third experiment using exactly the same previous controller, but, this time, placing two unknown masses in tandem attached to the ﬁrst controlled mass. The results are shown in Figure 8. 0 2 4 6 8 10 0 0.005 0.01 0.015 time [s] [m] 0 2 4 6 8 10 0 2 4 6 time [s] [N] x(t),x*(t) u(t) Fig. 6. Closed loop experimental response for the unperturbed controlled mass alone. 0 2 4 6 8 10 0 0.005 0.01 0.015 time [s] [m] 0 2 4 6 8 10 0 2 4 6 time [s] [N] x(t),x*(t) u(t) Fig. 7. Closed loop experimental response for the controlled mass perturbed by the attachment of a second unknown mass via unknown spring and damper. 0 2 4 6 8 10 0 0.005 0.01 0.015 time [s] [m] 0 2 4 6 8 10 0 2 4 6 time [s] [N] x(t),x*(t) u(t) Fig. 8. Closed loop experimental response for the controlled mass perturbed by the attachment of two unknown masses in tandem via unknown springs and dampers. B. Perturbation inputs arising from an inﬁnite dimensional system In view of the successful experimental performance of the closed loop ﬁnite dimensional perturbed mechanical system and the proposed robust GPI controller, we set out to repeat some of the previous experiments with an added complexity in the unknown perturbation signal generation. A rather ﬂexible appendage, topped with a signiﬁcant mass, was built and ﬁrmly attached to the top of one of the moving cars in the train as shown in the following picture. The experimental results regarding the controlled mass Fig. 9. Mass-spring-damper system with a ﬂexible appendage. e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 7 0 1 2 3 4 5 0 0.005 0.01 0.015 time [s] [m] 0 1 2 3 4 5 0 1 2 3 4 time [s] [N] x(t),x*(t) u(t) Fig. 10. Closed loop experimental response for the controlled mass perturbed by the attachment of two unknown masses in tandem via unknown springs and dampers and one ﬂexible appendage placed on the second mass. Fig. 11. Mass-spring-damper system with a ﬂexible appendage on the second and third carts. position and the applied control input force are depicted in Figure 10 Since the results were rather encouraging, we placed one such ﬂexible appendage on the second and third carts and proceeded to control the ﬁrst mass motion, as done before, with the same previously used controller. Figure 11 depicts the arrangement. Figure 12 depicts the corresponding controlled position and control input signals. 0 1 2 3 4 5 0 0.005 0.01 0.015 time [s] [m] 0 1 2 3 4 5 0 1 2 3 4 time [s] [N] x(t),x*(t) u(t) Fig. 12. Closed loop experimental response for the controlled mass perturbed by the attachment of two unknown masses in tandem via unknown springs and dampers and two ﬂexible appendages placed on the second and third carts. Fig. 13. Mass-spring-damper system with ﬂexible appendages on the three carts. 0 1 2 3 4 5 0 0.005 0.01 0.015 time [s] [m] 0 1 2 3 4 5 0 1 2 3 4 time [s] [N] x(t),x*(t) u(t) Fig. 14. Closed loop experimental response for the controlled mass perturbed by the attachment of two unknown masses in tandem via unknown springs and dampers and three ﬂexible appendage placed on the controlled mass and in the second and third carts. Finally, we placed a ﬂexible appendage on each one of the tree cars in the ECP system, as shown in the picture of Figure 13. The closed loop performance is depicted in Figure 14 For these experiments the values of the springs, dampers and cart masses were modiﬁed to allow for further oscillations. We set: k1 = 191.31 N/m, c1 = 3.64 N/m/s, m = 2.82 kg k2 = 391.16 N/m, c2 = 1.75 N/m/s, m2 = 2.59 kg k3 = 344.83 N/m, c3 = 1.75 N/m/s, m3 = 2.59 kg The controller gains were set to be ζ = 7, ωn = 70, p = 70. C. Robustness with respect to mass uncertainty As stated in the proposed robust output feedback GPI controller design, given by u = u∗ (t)−m k6s6 + k5s5 + · · · + k1s + k0 s5(s6 + k12s5 + · · · + k8s + k7) (x−x∗ (t)) the only parameter that needs to be known, with certitude, is the controlled mass parameter, m, associated with the ﬁrst cart. Clearly, it is possible that such a mass is not perfectly known. We carried out an experimental study on the effects ofe-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 8 Fig. 15. Position trajectories of controlled mass for different values of the ratio mc/m. Fig. 16. Control input trajectories of controlled mass for different values of the ratio mc/m. the additional uncertainty on the needed mass parameter value. Suppose we wrongly set the parameter m in the controller to the value mc and used instead the controller: u = u∗ (t)−mc k6s6 + k5s5 + · · · + k1s + k0 s5(s6 + k12s5 + · · · + k8s + k7) (x−x∗ (t)) with u∗ (t) = mc ¨x∗ (t). We performed a series of experiments, including a ﬂexible appendage on each of the carts, where the value of mc set in the controller software was made to vary from mc = 0.28 [Kg] (i.e. 10% of the actual mass value) to mc = 8.46 [Kg] (i.e., 300% of the actual mass value) in steps of 10 % of the ratio mc/m. The true value of m was known to be 2.82 [Kg]. For mc = 0.28 [Kg] the controller produces an unstable response of the system. For mc = 0.56 a stable but oscillatory is achieved. The response trajectories for each value of the ratio mc/m are depicted in Figure 15. In ﬁgure 16, the corresponding set of control input trajectories are shown. As the ratio mc/m exceeds the ideal value of 1, the controlled responses are less oscillatory while the control trajectories exhibit a noisy character. This is due to the high- gain effect of the values of the ratio mc/m on the root locus. It is easy to show that as mc/m is very small the roots are close to the origin with an angle of departure that makes the locus cross the imaginary axis towards the right half of the complex plane. There is therefore an interval of instability caused by the small values of the ratio mc/m. As the ratio grows, the root locus intersects back the imaginary axis and converges towards the stable location of the closed loop zeroes reaching them when mc/m = 1. As the ratio mc/m approaches “inﬁnity” the roots of the closed loop characteristic polynomial asymptotically tend towards the stable zeros at inﬁnity making the system more stable, faster, and hence, more sensitive with respect to high frequency measurement noises. In conclusion, these results demonstrate that the proposed output feedback control method is robust with respect to a wide range of uncertainty on the only parameter needed to be speciﬁed in the controller. V. CONCLUSION In this article we have proposed a dynamical output feed- back control, of the GPI type, for a reference trajectory tracking task of the position of a controlled mass attached to an unknown dynamical system of the mass-spring-dampers type. The controller is derived on the basis of a severely simpliﬁed mechanical system model contemplating only the controlled mass and a bounded, sufﬁciently smooth, perturbation input but otherwise of completely unknown nature. The actual con- trolled mass is subject to unknown but bounded perturbation inputs as arising from an uncertain dynamical subsystem of an arbitrary, unknown, number of tandem connected sliding masses via springs and dampers which is attached to the controlled system through a set of springs and dampers with unknown rigidity and viscosity coefﬁcients. The attachment of ﬂexible appendages, actually constituting inﬁnite dimen- sional systems contributing to the unknown perturbation input, does not change the perturbation rejection capabilities of the proposed output feedback control scheme while satisfactorily accomplishing the desired trajectory tracking control objective. The developed robust GPI controller is derived on the basis of the simpliﬁed second order system controlled mass model and the assumption of a polynomial family of perturbation in- puts of certain ﬁnite, but arbitrary, degree. The GPI controller adopts the form of a classical scalar compensation network processing the tracking error and producing the required feedback control input force. The performance of the de- signed controller was tested on a didactic ECP system using a Matlab Simulink programming facility. The experimental results indicate a remarkable performance of the designed feedback controller in the presence of a trajectory tracking task and completely unknown perturbations which include real Coulomb friction coefﬁcients. An experimental study of the robustness with respect to the resulting controller gain parameter when the mass of the controlled cart is uncertain was convincingly carried out with the presence of the ﬂexible appendages mounted on each one of the carts comprising the ECP system. A similar GPI controller, which now controls the position of the second, intermediate, mass in a set of three coupled masses, with the inclusion of a ﬂexible appendage (i.e., an inﬁnite dimensional system), ﬁrmly attached to the third mass, is now being pursued as a crucial test on the perturbation e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32 9 rejection capabilities of the class of proposed output feedback controllers. REFERENCES [1] J. Becedas, V. Feliu and H. Sira-Ram´ırez “GPI Control for a Single- Link Flexible Manipulator” International Conference on Modeling, Sim- ulation and Control (ICMSC’07). San Francisco, USA, 24-26 October, 2007. [2] F. Beltr´an Carbajal, G. Silva-Navarro and H. Sira-Ram´ırez, H., “Adaptive-like active vibration suppression for a nonlinear mechanical system using on line algebraic identiﬁcation”, The Thirteen International Congress on Sound and Vibration (ICSV13-Vienna), Vienna, Austria, July 2-6, 2006. [3] F. Beltr´an-Carbajal, G. Silva-Navarro, H. Sira-Ram´ırez and J. Quezada- Andrade, “Active vibration control using on-line algebraic identiﬁcation of harmonic vibrations” American Control Conference, 2005. Portland, Oregon, USA, June 8-10, 2005. [4] F. Beltr´an-Carbajal, G. Silva-Navarro and H. Sira-Ram´ırez, “Application of on-line algebraic identiﬁcation in active vibration control” Proceed- ings of the ISMA-2004, Conference on Noise and Vibration Engineering, Leuven, Belgium, September 20-22, 2004. [5] F. Beltr´an, H. Sira-Ram´ırez, G. Silva-Navarro, “Robust active vibration absorption using sliding modes, delta-modulators and generalized PI control” 10th International Congress on Sound and Vibration, July 7-10, 2003. Stockholm, Sweden. [6] M. Fliess, H. Sira-Ram´ırez, “An algebraic framework for linear identiﬁ- cation”. ESAIM Contr. Optim. and Calc. of Variat. Vol. 9, pp. 151-168, 2003. [7] M. Fliess, R. M´arquez and E. Delaleau, “State Feedbacks withou asymptotic observers and Generalized PID Regulators” in Nonlinear Control in the Year 2000, A. Isidori,, F. Lamnabhi-Lagarrigue and W. Respondek (Eds.), Lecture Notes in Control and Information Sciences, Vol 258, pages 367-384. Springer-Verlag, London, 2000. [8] M. Fliess, R. Marquez, E. Delaleau and H. Sira-Ram´ırez, “ Correcteurs Proportionnels-Int`egraux G´en´eralis´es, ESAIM: Control, Optimization and Calculus of Variations, Vol. 7, No. 2, pp. 23-41, 2002. [9] A. Franco-Gonz´alez, R. M´arquez and H. Sira-Ram´ırez “On the Generalized-Proportional-Integral Sliding mode Control of the ”Boost- Boost” Converter” International Conference on Electrical and Elec- tronics Engineering (ICEEE-2007), Ciudad de M´exico, September 5-7, 2007. [10] V. Hern´andez, H. Sira-Ram´ırez “On the robustness of generalized PI control with respect to parametric uncertainties” 2003 European Control Conference, Cambridge, England U.K., September 2003. [11] V. M. Hern´andez and H. Sira-Ram´ırez, “Generalized PI control for global robust position regulation of rigid robot manipulators” 2003 American Control Conference. Denver Colorado, June 2003. [12] V. M. Hern´andez and H. Sira-Ram´ırez, “Generalized PI control for swinging up and balancing the inertia wheel pendulum” 2003 American Control Conference. Denver Colorado, June 2003. [13] W. J. Rugh, “Linear System Theory” (2nd ed.), Prentice-Hall Inc. Upper Saddle River, New Jersey, USA. 1996. [14] H. Sira-Ram´ırez and R. Silva-Ortigoza,Control Design Techniques in Power Electronics Devices, Springer-Verlag, Power Systems Series, London, 2006. ISBN: 1-84628-458-9. [15] H. Sira-Ram´ırez and G. Silva-Navarro “Generalized PID control of the Average Boost Converter” in Adaptive and Nonlinear Control NCN4, 2001. A. Zinober and D. Owens (Eds.), Springer-Verlag, London, 2003, pp. 301-310. [16] H. Sira-Ram´ırez y G. Silva-Navarro, “ Regulation and Tracking for the Average Boost Converter Circuit: A Generalized Proportional Integral Approach” International Journal of Control Vol. 75, No. 13, pp. 988- 1001, September 2002. [17] J.R. Trapero, H. Sira-Ram´ırez and V. Feliu Batlle, “A fast on-line frequency estimator of lightly damped vibrations in ﬂexible structures” Journal of Sound and Vibration, Vol. 307, pp. 365-378, 2007. e-STA copyright 2008 by SEE Volume 5, N°4, pp 24-32